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Registered Member #95
Joined: Thu Feb 09 2006, 04:57PM
Location: Norway
Posts: 1308
Actually I used IRFP450s, each doubled up. SO, 18A peak or 13A RMS shared (hopefully) between two mosfets with an rds of 0,44R. That's about 20W of power dissipation per device, but since they only conduct for half the time we'll say 15W. (Switching losses play in as well.) Giving 60W of power lost in the fets. It's important to note that:
1) This is power LOST in the MOSFETs, the only way it affects output power is whether it approaches the maximum of what the IRFP450s can handle. 2) The 18A circulate in the tank/inverter loop and is largely reactive current, the actual current drawn from mains is probably 3-5A.
Registered Member #1838
Joined: Tue Dec 02 2008, 06:01PM
Location:
Posts: 38
I obviously have a huge gap in my understanding of the FET specs. If I look at the save operating area graph of the IRFP460, at 300V (drain to source) a dc value of about 0.7A can be drawn continuously? Thus for a 50% duty cycle it must be about 1.7A per FET. Can someone please refer my to a webpage that can help to explain.
Registered Member #30
Joined: Fri Feb 03 2006, 10:52AM
Location: Glasgow, Scotland
Posts: 6706
The beauty of switched-mode power is that the FET is either off or on. (Anything in between - part on or part off - is not switched mode, but linear operation, which went out of fashion in the 1970s.)
When it's off, it has a high voltage across it, but no current flowing, therefore the power dissipated is zero. (Power is voltage times current, and anything multiplied by zero is zero.)
When it's on, it has a high current flowing, but no voltage across it. (We assume Rds(on) is so small that the IR drop is negligible.) So the power dissipated is again zero.
So this means a switched-mode circuit can pass infinite power without getting hot
Well not exactly, but it means that it can handle far more than what you said, because the 300V and 1.7A are never present at the same time. I would expect a fullbridge of IRFP460s to deliver a couple of kilowatts at hobbyist levels of reliability, while dissipating roughly the 50W or so of heat that Uzzors suggested.
Registered Member #95
Joined: Thu Feb 09 2006, 04:57PM
Location: Norway
Posts: 1308
For the love of god, my inverter uses IRFP4 -> 50 <- mosfets. Not IRFP460, so everyone stop bringing them up.
Now Raka, the maximum drain current specified in mosfet datasheets is DC current. Currents beyond this heat the junction (inside the mosfet package) faster than heat can be removed from the package. This has to do with thermal resistance. For all practical use the junction temperature is what limits the mosfet's current rating. You seem to have Ohm's law down, but not generel circuit analysis.
The following example applies to a single IRFP450, and isn't related to the inverter. It's just food for thought.
When mosfets are used in switching applications like this, they can be thought of as switches with some resistance, in this case 0,4 ohms. Now apply Ohm's Law to the switch. 0,4R * 14A = 5,6V So the voltage across the mosfet is only 5,6V when it's on and actually passing current. That means the dissipation in the conducting mosfet has to be 78W. The rest of the 300 - 5,6 = 294,4V are across the load, which I'll call LOAD. The power dissipated in LOAD is 294,4V * 14A = 4kW. When the mosfet is off the resistance is astronomic, and the full 300V will be across it. However, since no current flows through the mosfet the power dissipated in it has to be 0W. Is it any clearer?
Registered Member #1838
Joined: Tue Dec 02 2008, 06:01PM
Location:
Posts: 38
Ok, another question: In a setup like yours, with FET’s in paralleled. What is the pros and cons of a winding for each FET on the gate drive transformer or just one winding for the high side and one winding for the low side, driving more than one FET with a winding?
Registered Member #95
Joined: Thu Feb 09 2006, 04:57PM
Location: Norway
Posts: 1308
The simplest approach is to simply parallel the mosfets and then consider them a single larger mosfet. The gate capacitance will be larger, the current handling roughly the same, but the power dissipation will be halved. I found that the gate driver had no problem driving twice the capacitance fast enough. Unless the switching waveforms become unreasonably sloped, there is little point in using a second GDT with separate gate drivers to power the other set of mosfets. If you're thinking of using four secondary windings and putting pairs in parallel, that will only reduce the resistance of the secondary, which is often negligible to start with.
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